Forum » Pomoč in nasveti » Pomoč pri prevodu tehničnega "štromarskega" besedil
Pomoč pri prevodu tehničnega "štromarskega" besedil
Dejan_007 ::
Ker mi znanje tehničnega besedila dela velike preglavice bi nekoga lepo prosil, če bi mi lahko prevedel sledečo besedilo:
According to Fig.8a the MCS is implemented as an active current mirror [7] formed by a current measurement shunt RSH, an operational amplifier (OPA) O1 with feed-back path kI ⋅RSH and a small-signal NPN transistor Q1. Due to its single-quadrant operation, the linear-mode power amplifier can be realized using only a single NPN power transistor Q2 in emitter-follower configuration driven by OPA O2. In the final prototype (Fig.8b) the module’s short circuit current is programmed by the PNP-transistor current source feeding the diode chain (16x 1N4148) to (5.6V−0.6V)/1.5kΩ = 3.33mA leading to ISC = 3.33A as a consequence of the 1:1000 current mirror(kI = 1mA/A, defined by the resistor ratio 0.1Ω/100Ω). For the power transistor a Darlington-type (TIP142) is used which can be driven directly by O2 due to its high current gain. In order to protect Q2 in case of short circuit, a current limiter (BC547B) is added to its base-emitter path. As power supply VB no more laboratory equipment is necessary, a simple industrial SMPS will be adequate. It has to be considered, however, that the selected OPA LM358 (although allowing ground-referenced current measurement as needed for O1) shows a noticeable positive supply voltage margin (≈3V). This effect is further enhanced by the base-emitter voltage of Q2 (≈1.2V due to the Darlington principle). Consequently, a supply voltage of VB ≈ 26V is required to achieve the aimed VOC = 21.7V. The application of a true railto-rail OPA in connection with a compound Darlington transistor opens a possibility for reducing this voltage “headroom” which worsens the efficiency of the circuit. Alternatively, also a separate (increased) power supply for the OPA would be feasible as known, e.g., from audio power amplifiers, complicating, however, the SMPS design. The driving stage O2 is configured as a differential amplifier in order to suppress the 3V “base voltage” of the diode chain provided by the zener diode C3V0 and which is required to guarantee sufficient collector-emitter voltage for Q1. The voltage gain of the power amplifier is set to kV = 2 by the resistor pairs 33kΩ/ 66kΩ. With this, 16 pcs. of 1N4148 have been found adequate for achieving VOC = 21.7V. Finally, it should be mentioned that the 22nF capacitor across the diodes and, especially, the 220μF electrolytic capacitor at the output are necessary to prevent parasitic ringing.
The measurement values taken from the series-mode laboratory prototype simulator (realized similar as shown in Fig.6d for the amplified diode concept) unfortunately match the real KC50T module in an only suboptimal manner (Fig.9a). On contrary to ISC and VOC (which are fixed by the dimensioning) a noticable deviation exists near the MPP region. Obviously this is a drawback of modeling a solar cell by a small-signal diode like 1N4148 at low current rates. Furthermore, also the efficiency behavior of the series-mode simulator is somewhat disappointing. As indicated in Fig.9b good efficiency rates appear in the “no-load region” V ≈ VOC (for all series-mode regulators η increases proportional to the output voltage ηSER = V/VB). However, already near MPP the efficiency of the shunt-mode simulator significantly exceeds the series-mode circuit. Remark: For common PV modules VMPP ≈ 0.75VOC is valid typically. Assuming about 20% voltage headroom (i.e., VB = 1.2VOC) gives an efficiency of only 0.75/1.2=62% at MPP in comparison to approximately 85% for the shunt-mode simulator. For improving ηSER at lower ratings of V, it would be thinkable to pre-regulate VB to lower the voltage drop across Q2 as is known from advanced linear power amplifiers [8]. Due to the high effort, this solution shall not be pursued here, however.
Že v naprej se zahvaljujem
HVALA
According to Fig.8a the MCS is implemented as an active current mirror [7] formed by a current measurement shunt RSH, an operational amplifier (OPA) O1 with feed-back path kI ⋅RSH and a small-signal NPN transistor Q1. Due to its single-quadrant operation, the linear-mode power amplifier can be realized using only a single NPN power transistor Q2 in emitter-follower configuration driven by OPA O2. In the final prototype (Fig.8b) the module’s short circuit current is programmed by the PNP-transistor current source feeding the diode chain (16x 1N4148) to (5.6V−0.6V)/1.5kΩ = 3.33mA leading to ISC = 3.33A as a consequence of the 1:1000 current mirror(kI = 1mA/A, defined by the resistor ratio 0.1Ω/100Ω). For the power transistor a Darlington-type (TIP142) is used which can be driven directly by O2 due to its high current gain. In order to protect Q2 in case of short circuit, a current limiter (BC547B) is added to its base-emitter path. As power supply VB no more laboratory equipment is necessary, a simple industrial SMPS will be adequate. It has to be considered, however, that the selected OPA LM358 (although allowing ground-referenced current measurement as needed for O1) shows a noticeable positive supply voltage margin (≈3V). This effect is further enhanced by the base-emitter voltage of Q2 (≈1.2V due to the Darlington principle). Consequently, a supply voltage of VB ≈ 26V is required to achieve the aimed VOC = 21.7V. The application of a true railto-rail OPA in connection with a compound Darlington transistor opens a possibility for reducing this voltage “headroom” which worsens the efficiency of the circuit. Alternatively, also a separate (increased) power supply for the OPA would be feasible as known, e.g., from audio power amplifiers, complicating, however, the SMPS design. The driving stage O2 is configured as a differential amplifier in order to suppress the 3V “base voltage” of the diode chain provided by the zener diode C3V0 and which is required to guarantee sufficient collector-emitter voltage for Q1. The voltage gain of the power amplifier is set to kV = 2 by the resistor pairs 33kΩ/ 66kΩ. With this, 16 pcs. of 1N4148 have been found adequate for achieving VOC = 21.7V. Finally, it should be mentioned that the 22nF capacitor across the diodes and, especially, the 220μF electrolytic capacitor at the output are necessary to prevent parasitic ringing.
The measurement values taken from the series-mode laboratory prototype simulator (realized similar as shown in Fig.6d for the amplified diode concept) unfortunately match the real KC50T module in an only suboptimal manner (Fig.9a). On contrary to ISC and VOC (which are fixed by the dimensioning) a noticable deviation exists near the MPP region. Obviously this is a drawback of modeling a solar cell by a small-signal diode like 1N4148 at low current rates. Furthermore, also the efficiency behavior of the series-mode simulator is somewhat disappointing. As indicated in Fig.9b good efficiency rates appear in the “no-load region” V ≈ VOC (for all series-mode regulators η increases proportional to the output voltage ηSER = V/VB). However, already near MPP the efficiency of the shunt-mode simulator significantly exceeds the series-mode circuit. Remark: For common PV modules VMPP ≈ 0.75VOC is valid typically. Assuming about 20% voltage headroom (i.e., VB = 1.2VOC) gives an efficiency of only 0.75/1.2=62% at MPP in comparison to approximately 85% for the shunt-mode simulator. For improving ηSER at lower ratings of V, it would be thinkable to pre-regulate VB to lower the voltage drop across Q2 as is known from advanced linear power amplifiers [8]. Due to the high effort, this solution shall not be pursued here, however.
Že v naprej se zahvaljujem
HVALA
- spremenil: Dejan_007 ()
Zheegec ::
Ja, some one should do all the work for you
Imaš težave s kakšno specifično besedo ali besedno zvezo?
Imaš težave s kakšno specifično besedo ali besedno zvezo?
"božja zapoved pravi; <Spoštuj očeta in mater>,
ne govori pa o spoštovanju sodstva."
Janez Janša, 29.04.2014
ne govori pa o spoštovanju sodstva."
Janez Janša, 29.04.2014
Zgodovina sprememb…
- spremenil: Zheegec ()
Dejan_007 ::
V napačno rubriko sem napisal (HVALA :)). Imam probleme z povezovanjem tehničnih besed v stavkih, Upam pa da mi bo res kdo lahko tole prevedel, če si bo vzel toliko časa.
Zgodovina sprememb…
- spremenil: Dejan_007 ()
roscha ::
Po Fig.8a MCS se izvaja kot dejavni ogledalo [7], ki ga sestavljajo sedanji shunt za merjenje RSH, operacijski ojačevalnik (OPA) O1 s povratnimi pot KI ? RSH in NPN mali signal tranzistor Q1. Zaradi svoje enem kvadrantu operacijo lahko moč linearno-mode ojačevalnik se izvajajo s samo enim NPN tranzistor Q2 moči v konfiguraciji onesnaževalec-Partizan poganja OPA O2. V zadnji prototip (Fig.8b) modula toka kratkega stika je programirana s PNP-tranzistor trenutni vir hranjenja diode verige (16x 1N4148) do (5.6V-0.6V) / 1.5k? = 3.33mA vodi k ISC = 3,33 kot posledica trenutne 1:1000 ogledalo (Ki = 1MA / A, ki jih določi upor razmerje 0.1?/100?). Za moč tranzistor je Darlington tipa (TIP142) se uporabljajo, ki se lahko neposredno poganja O2 zaradi visoke trenutni dobiček. Da bi zaščitili Q2 v primeru kratkega stika, je toka (BC547B) doda svojo pot osnovno-oddajnik. Kot napajanje VB ni več laboratorijsko opremo je potrebno, bo preprosto industrijsko SMPS primerna. Treba je seveda upoštevati, da izbrana OPA LM358 (čeprav omogoča zemlji navaja merjenje toka, kot je potrebno za O1) kaže opazno pozitivno stopnjo napetosti (? 3 V). Ta učinek je še podkrepil z napetostjo osnovo onesnaževalec Q2 (? 1,2 V zaradi načela Darlington). Zato je napetost v VB ? 26V, potrebne za dosego za VOC = 21.7V. Uporaba pravega OPA railto-rail v zvezi s spojino Darlington tranzistor odpira možnost za zmanjšanje te napetosti "višina", ki poslabšuje učinkovitost tokokroga. Lahko pa bi tudi ločeno (povečano) napajanje za OPA izvedljivo kot je znano, na primer, od avdio ojačevalniki moči, zapleta pa design PTM. Vožnja odru O2 je konfiguriran kot diferencialnim ojačevalcem, da bi odstranila 3V "osnovno napetost" iz diode verige, ki jih C3V0 Zener diodo in ki so potrebne za zagotovitev zadostnih napetost kolektor-oddajnik za Q1. Napetost dobiček ojačevalnika je nastavljena na kV = 2, ki ga upor pari 33k? / 66k?. S tem, 16 kosov. od 1N4148 je bilo ugotovljeno, primerna za doseganje VOC = 21.7V. Nazadnje je treba omeniti, da 22nF kondenzator preko diode, predvsem pa 220?F elektrolitski kondenzator na izhodu so potrebni za preprečitev motečega zvonjenja.
Vrednosti meritev, vzetih iz laboratorijskega serije-mode simulator prototip (spoznal podobno kot je prikazano v Fig.6d za pomnožene koncept diode) žal ustreza dejanskim modul KC50T v le najučinkovitejši način (Fig.9a). Na nasprotju z ISC in VOC (ki so bili določeni z dimenzioniranje) opazen odmik obstaja v bližini MPP regiji. Očitno je to pomanjkljivost modeliranja sončne celice, ki jih diode mali signal kot 1N4148 pri nizkih tekočih cenah. Poleg tega je tudi učinkovitost obnašanje simulator serije-mode je nekoliko pod pričakovanji. Kot je navedeno v Fig.9b visoke stopnje učinkovitosti se pojavljajo v "no-load regiji" V ? VOC (za vse serije-mode regulatorji ? povečuje sorazmerno z izhodno napetost ?SER = V / VB). Vendar pa je že blizu MPP učinkovitost simulator shunt-mode znatno presega vezje serije-mode. Opomba: Za skupne module PV VMPP ? 0.75VOC velja običajno. Ob predpostavki, da približno 20% napetosti headroom (tj., VB 1.2VOC =) omogoča izkoristek le 0.75/1.2 = 62% na MPP v primerjavi s približno 85% za simulator shunt-mode. Za izboljšanje ?SER pri nižjih ocen V, bi bilo vendarle mogoča vnaprej urediti VB za znižanje padca napetosti v Q2, kot je znano iz zahtevnejšimi linearnimi ojačevalniki moči [8]. Zaradi velikega napora, ta rešitev ne sme biti tukaj izvajajo, vendar.
Evo sem si vzel toliko časa :) copy/paste -> GUGL translate skrpucalo.
Kdor je toliko neumen da ti gre tole za zabavo prevajat: naj izvoli. Za povrh še na "suho" brez slik. Nimaš šans. Danes bi junci vse radi na pladnju, pa da nekdo drug naredi.
Zašvicaj malo, ti ne bo škodovalo!
Vrednosti meritev, vzetih iz laboratorijskega serije-mode simulator prototip (spoznal podobno kot je prikazano v Fig.6d za pomnožene koncept diode) žal ustreza dejanskim modul KC50T v le najučinkovitejši način (Fig.9a). Na nasprotju z ISC in VOC (ki so bili določeni z dimenzioniranje) opazen odmik obstaja v bližini MPP regiji. Očitno je to pomanjkljivost modeliranja sončne celice, ki jih diode mali signal kot 1N4148 pri nizkih tekočih cenah. Poleg tega je tudi učinkovitost obnašanje simulator serije-mode je nekoliko pod pričakovanji. Kot je navedeno v Fig.9b visoke stopnje učinkovitosti se pojavljajo v "no-load regiji" V ? VOC (za vse serije-mode regulatorji ? povečuje sorazmerno z izhodno napetost ?SER = V / VB). Vendar pa je že blizu MPP učinkovitost simulator shunt-mode znatno presega vezje serije-mode. Opomba: Za skupne module PV VMPP ? 0.75VOC velja običajno. Ob predpostavki, da približno 20% napetosti headroom (tj., VB 1.2VOC =) omogoča izkoristek le 0.75/1.2 = 62% na MPP v primerjavi s približno 85% za simulator shunt-mode. Za izboljšanje ?SER pri nižjih ocen V, bi bilo vendarle mogoča vnaprej urediti VB za znižanje padca napetosti v Q2, kot je znano iz zahtevnejšimi linearnimi ojačevalniki moči [8]. Zaradi velikega napora, ta rešitev ne sme biti tukaj izvajajo, vendar.
Evo sem si vzel toliko časa :) copy/paste -> GUGL translate skrpucalo.
Kdor je toliko neumen da ti gre tole za zabavo prevajat: naj izvoli. Za povrh še na "suho" brez slik. Nimaš šans. Danes bi junci vse radi na pladnju, pa da nekdo drug naredi.
Zašvicaj malo, ti ne bo škodovalo!
Okapi ::
Zastonj ti tega ne bo nihče prevedel, za 50 evrov boš pa sigurno našel kakšnega prevajalca.
O.
O.
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